4.3 Mixer
5.2.6 Benchmarks and Discussion
2-Channel Receiver
100 200 300 400 500
0 2 4 6 8 10 12 14
IF [MHz]
ConversionGain[dB]
Channel1 Channel2
calculated with IF amplifier
Figure 5.14: 2-Channel RX Measured Conversion Gain vs. IF
Receiver Integration
Table 5.4: Comparison of 77 GHz SiGe HBT-based Receiver Front-Ends Node ft, fmax ffmax
center NFSSB Gain iP1dB PDC Area Integrationa
Size
[µm] [GHz] [dB] [dB] [dBm] [mW] [mm2]
This Work
0.25 180, 220 2.9 12.6 10 -10.4 40.3 1.74 (LNA, BALUNs, Mixer; Flip-Chip) This
Work
0.25 180, 220 2.9 16.5 12.1 -11.4 132 5.4 2-Ch. RX: (LNAs, BALUNs, Mixers, LO-Splitter; Flip-Chip)
[106] 0.25 180, 220 2.9 10.2b 21.7 -35 345 0.5 (LNA, BALUNs, Mixer, IF-buf.)
[3] 0.13 207, 285 3.7 12 37 <-30 100 2.5 (LNA, Mix., IF-Amp, Mix., BB-Amp.)
[46] 0.18 180, 200 2.6 11 31 -30.7 162.5 2.4 I-Q RX: (LNA, Mix., VGA)
[22] 0.35 200, 275 3.6 11 28 -16 1073 1.1 I-Q RX: (LNA, BALUNs, Hybrid, Mix.)
[77] 0.13 210, 280 3.6 11.5 40 <-40 195 1.7 (LNA, Mix., VCO)
[73] 0.13 170, 200 2.6 12 25.6 -24 120 0.4 (LNA, Mix., IF-Amp.)
[54] 0.13 200, 250 3.2 14 24 -10 132 0.75 (LNA, Mix.)
[97] 0.18 200, 200 2.6 13 24 -7.8 238 1.12 (BALUN, Mix., IF-Buf.)
[74] 0.13 220, 250 3.2 7.8 24 -21.7 123 0.24 (LNA, Mix., IF-Amp.)
a1 Channel RX, unless explicitly noted.
bSimulated value.
2-Channel Receiver
The realized front-end performance in main categories (such as noise figure, linearity, gain and DC consumption) resembles most the front-end in [51]. Interestingly, [51] is a front-end in 65 nm CMOS. The front end in [51] also consumes lowest area due to extensive deployment of inductors (as opposed to longer microstrip transmission lines, some of which areλ/4 in this design).
Table 5.5: Comparison of 77 GHz CMOS FET-based 1-Channel Receiver Front-Ends
Node NFSSB Gain iP1dB PDC Area Integration Size
[nm] [dB] [dB] [dBm] [mW] [mm2]
[51] 65 12 13 -16 89 0.24 (LNA, BALUNs,
Mixer, IF-Buf.)
[50] 90 10 8 n.a. 260 0.55 (LNA, BALUNs,
Buffers, Mixer, IF-Buf.)
[60] 65 11.4 38 <-30 45 0.5 (LNA, Mixer, IF-Buf.)
[71] 90 15.6 23.1 n.a. 111 1.2 (BALUN, LNA,
Mixer, IF-, LO-Buf.)
[59] 65 12.2 33.7 -32 16.9 0.52 (LNA, Mixer, LO BALUN)
127
6 Conclusions
This work presents a systematical analysis and design procedure of an integrated millimeter-wave high performance, low power multi-channel receiver operating at fmax3 in SiGe for auto-motive LRR. The low-gain high-linearity LNA design approach applied in this work allowed paradigm shift from either a high-linearity (and high noise) or a low-noise (and poor linearity) front-end to a finer trade-off between both performance criteria.
In the case of the mixer the conventional approach of design for high gain was modified, too. A high gain mixer, one one hand, would facilitate suppressing the IF stages’ noise contributions.
On the other hand, in this application a high gain mixer would overdrive the IF buffer / ADC converter. The overall front end linearity would be compromised as a result. Thus, mixer target specs were redefined as low-gain, low-noise and high-linearity. Additionally, the LNA was re-used as the mixer’s transconductance stage. This decision offered the following benefits:
transconductance stage (TRC) input match improved mixer’s conversion gain, a 50 Ω output match resonated out the unmatched transistor’s output capacitance. Traditional DC-coupling between transconductance and mixer core (as in case of Gilbert cell) would result in half of the TRC transistor DC-current flowing through each core transistor. This would set constraints on both the current and the TRC and the core sizings, which ideally should be design parameters.
Additionally, TRC and core stacking would mean voltage headroom limitation to both. AC-coupling came to break out of these trade-offs: the TRC was sized, designed and biased for low noise and the core for linearity and low noise; and the full headroom was made available to both mixer stages (excluding the resistive load).
Special attention was paid to the design of the transformer baluns. The resulting balun perfor-mance allowed relaxing the common-mode rejection requirements from the LNA and the mixer and yielded an additional performance improvement (by avoiding the additional stacking of current sources / sinks / resonators).
The forementioned circuit components were integrated into a 2 channel low-IF homodyne re-ceiver. The LO was distributed by an active buffered in-phase LO power splitter. Several isolation techniques were deployed. The measured isolation between the two receive channels exceeded 35 dB. The measured 2-, 1-channel receivers and the mixer have comparable perfor-mance to the published state-of-the-art results in SiGe technology (despite using the “slowest”
technology among the benchmarks). Important to stress the record-low DC consumption – 132 mW, 40.3 mW and 34.6 mW, respectively, which is circa 18 of the consumption of the similarly performing SiGe receiver in [22]. The power consumption is on par with that of a 65 nm CMOS front-end with comparable performance [51]. In the automotive case there is a very tight budgeting of the available power and with hybrid/electrical cars the available power
129
Conclusions
for the driving assist systems is going to shrink further, so the achieved low DC consumption is a welcome feature.
For further development of the receiver, the following approaches should be investigated:
Shrinkage of the LNA input match. The area of the LNA was large mostly due to a series λ/4 line. To reduce the layout size this line either can be bent or a different input matching topology could be investigated (for example as used in the LO Splitter).
Incorporation of transformer. The transformer was realized as a stand-alone circuit only.
The 2-channel receiver required 4 baluns, so if the rat-race couplers are exchanged by the transformers considerable area reduction can be achieved.
Alternative approach to LO Splitter. The realized fully active LO Splitter involved complex custom design. To reduce the risk, to allow better modularity and designability an alternative approach to LO splitting between the RX channels can be of benefit.
The operation of a double-balanced mixer is retained if LO signal reverses it phase. This observation implies replacement of the in-phase LO Splitter by an anti-phase LO Splitter.
The anti-phase LO Splitter can be realized by re-using of the same transformer circuit (if amplification is needed – it can be added either at the transformer input and / or output by gain stages, such as LNA).
Mixer-only receiver. Since the realized LNA gain is low, deployment of a single LNA / several LNA stages was considered in section 5.1.2. The LNA addition improves the overall receiver noise figure, while impairing the receiver linearity. A different approach of totally removing the LNA stages while deploying a low-noise high-linearity mixer is a very interesting alternative that could be studied further.
As next step, the presented high performance receiver can be realized in the BiCMOS technol-ogy and further integrated with an analog baseband, power management and digital baseband processing circuit blocks. The digital signal processing of the radar signals may profit by possi-bility of high level integration in CMOS and considerably lower power consumption compared to bipolar logic. This opens an opportunity for more flexible digitally intensive modulation schemes, such as phase-modulated continuous wave (PMCW). As well, this will result in a competitive, inexpensive, low-power, highly-integrated multichannel commercial solution. It can be applicable, in addition to automotive long range radar in other demanding industrial and consumer applications, among which are imaging systems, sensors, communication sys-tems, such as point-to-point (microwave relay links, two-way radio) and point-to-multipoint (long-range wireless backhaul links, broadcasting).
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